LMC660CN/NOPB National Semiconductor, LMC660CN/NOPB Datasheet - Page 7

• Manufacturer Part Number: LMC660CN/NOPB
• Description: IC OP AMP QUAD CMOS 14-DIP
• Manufacturer: National Semiconductor

Specifications of LMC660CN/NOPB

• Amplifier Type: General Purpose
• Number Of Circuits: 4
• Output Type: Rail-to-Rail
• Slew Rate: 1.1 V/µs
• Gain Bandwidth Product: 1.4MHz
• Current - Input Bias: 0.002pA
• Voltage - Input Offset: 1000µV
• Current - Supply: 1.5mA
• Current - Output / Channel: 40mA
• Voltage - Supply, Single/dual (±): 4.75 V ~ 15.5 V, ±2.38 V ~ 7.75 V
• Operating Temperature: 0°C ~ 70°C
• Mounting Type: Through Hole
• Package / Case: 14-DIP (0.300", 7.62mm)
• Bandwidth: 1.4 MHz
• Channel Separation: 130
• Common Mode Rejection Ratio: 83
• Current, Input Bias: 0.002 pA
• Current, Input Offset: 0.001 pA
• Current, Output: 40 mA
• Current, Supply: 0.75 mA
• Harmonic Distortion: 0.01 %
• Impedance, Thermal: 101 °C/W
• Number Of Amplifiers: Dual
• Package Type: MDIP-8
• Resistance, Input: 1 Teraohms
• Temperature, Operating, Range: 0 to +70 °C
• Voltage, Gain: 2000 V/mV
• Voltage, Input: 4.75 to 15.5 V
• Voltage, Noise: 22 nV/sqrt Hz
• Voltage, Offset: 1 mV
• Voltage, Output, High: 14.63 V
• Voltage, Output, Low: 0.26 V
• Voltage, Supply: 5 V
• Number Of Channels: 4
• Voltage Gain Db: 126.02 dB
• Common Mode Rejection Ratio (min): 63 dB
• Input Offset Voltage: 6 mV at 5 V
• Operating Supply Voltage: 5 V, 9 V, 12 V, 15 V
• Supply Current: 2.7 mA at 5 V
• Maximum Operating Temperature: + 70 C
• Minimum Operating Temperature: 0 C
• Lead Free Status / RoHS Status: Lead free / RoHS Compliant
• -3db Bandwidth: -
• Lead Free Status / Rohs Status: RoHS Compliant part Electrostatic Device
• Other names: *LMC660CN; *LMC660CN/NOPB; LMC660; LMC660CN

Application Hints
AMPLIFIER TOPOLOGY
The topology chosen for the LMC660, shown in Figure 1, is
unconventional (compared to general-purpose op amps) in
that the traditional unity-gain buffer output stage is not used;
instead, the output is taken directly from the output of the
integrator, to allow rail-to-rail output swing. Since the buffer
traditionally delivers the power to the load, while maintaining
high op amp gain and stability, and must withstand shorts to
either rail, these tasks now fall to the integrator.
As a result of these demands, the integrator is a compound
affair with an embedded gain stage that is doubly fed forward
(via C
driver. In addition, the output portion of the integrator is a
push-pull configuration for delivering heavy loads. While
sinking current the whole amplifier path consists of three
gain stages with one stage fed forward, whereas while
sourcing the path contains four gain stages with two fed
forward.
The large signal voltage gain while sourcing is comparable
to traditional bipolar op amps, even with a 600Ω load. The
gain while sinking is higher than most CMOS op amps, due
to the additional gain stage; however, under heavy load
(600Ω) the gain will be reduced as indicated in the Electrical
Characteristics. Avoid resistive loads of less than 500Ω, as
they may cause instability.
COMPENSATING INPUT CAPACITANCE
The high input resistance of the LMC660 op amps allows the
use of large feedback and source resistor values without
losing gain accuracy due to loading. However, the circuit will
be especially sensitive to its layout when these large-value
resistors are used.
Every amplifier has some capacitance between each input
and AC ground, and also some differential capacitance be-
tween the inputs. When the feedback network around an
amplifier is resistive, this input capacitance (along with any
additional capacitance due to circuit board traces, the
socket, etc.) and the feedback resistors create a pole in the
feedback path. In the following General Operational Amplifier
circuit,Figure 2 the frequency of this pole is
where C
including amplifier input capacitance and any stray capaci-
tance from the IC socket (if one is used), circuit board traces,
FIGURE 1. LMC660 Circuit Topology (Each Amplifier)
f
and C
S
is the total capacitance at the inverting input,
ff
) by a dedicated unity-gain compensation
00876704
7
etc., and R
formula, as well as all formulae derived below, apply to
inverting and non-inverting op amp configurations.
When the feedback resistors are smaller than a few kΩ, the
frequency of the feedback pole will be quite high, since C
generally less than 10 pF. If the frequency of the feedback
pole is much higher than the “ideal” closed-loop bandwidth
(the nominal closed-loop bandwidth in the absence of C
the pole will have a negligible effect on stability, as it will add
only a small amount of phase shift.
However, if the feedback pole is less than approximately 6 to
10 times the “ideal” −3 dB frequency, a feedback capacitor,
C
ing input of the op amp. This condition can also be stated in
terms of the amplifier’s low-frequency noise gain: To main-
tain stability a feedback capacitor will probably be needed if
where
is the amplifier’s low-frequency noise gain and GBW is the
amplifier’s gain bandwidth product. An amplifier’s low-
frequency noise gain is represented by the formula
regardless of whether the amplifier is being used in inverting
or non-inverting mode. Note that a feedback capacitor is
more likely to be needed when the noise gain is low and/or
the feedback resistor is large.
If the above condition is met (indicating a feedback capacitor
will probably be needed), and the noise gain is large enough
that:
the following value of feedback capacitor is recommended:
If
the feedback capacitor should be:
F
, should be connected between the output and the invert-
P
is the parallel combination of R
F
and R
www.national.com
IN
. This
S
S
is
),