LM2640MTC-ADJ National Semiconductor, LM2640MTC-ADJ Datasheet - Page 15

• Manufacturer Part Number: LM2640MTC-ADJ
• Description: Dual Adjustable Step-Down Switching Power Supply Controller
• Manufacturer: National Semiconductor

Application Information
The values of compensation components will be: C10 =
2200 pF, R11 = 8.2k, and C12 will not be used. Using this
data, the poles and zeros are calculated:
Using these values, the calculated gain plot is shown in Fig-
ure 6 .
Looking at the plot, it can be seen that the unity-gain cross-
over frequency f
value, the phase margin at the point is calculated to be about
84˚.
To verify the accuracy of these calculations, the circuit was
bench tested using a network analyzer. The measured gain
and phase are shown plotted in Figure 7 .
FIGURE 6. Calculated Gain Plot for 3.3V/4A Application
R13 = 20 m
L2 = 10 µH
R
DC gain = 55 dB
f
f
f
f
f
p
z
p
z
p
FIGURE 7. Measured Gain/Phase Plot for 3.3V/4A
L
(C10) = 1 / [2 X C10 (R11 + 160k) ] = 430 Hz
(R11) = 1 / [2 X R11 (C10 + C12) ] = 8.8 kHz
(C
(ESR) = 1 / [2 X ESR X C
(HF)
= 0.825
OUT
z
) = 1 / [2 X R
40 kHz
c
is expected to be about 25 kHz. Using this
Application
L
X C
OUT
OUT
] = 960 Hz
] = 27 kHz
(Continued)
DS100148-7
DS100148-8
15
The measured gain plot agrees very closely to the predicted
values. The phase margin at 0 dB is slightly less than pre-
dicted (71˚ vs. 84˚), which is to be expected due to the nega-
tive phase shift contributions of high frequency poles not in-
cluded in this simplified analysis.
It should be noted that 70˚ phase margin with 25 kHz band-
width is excellent, and represents the optimal compensation
for this set of values for V
Optimizing Stability
The best tool for measuring both bandwidth and phase mar-
gin is a network analyzer. If this is not available, a simple
method which gives a good measure of loop stability is to ap-
ply a minimum to maximum step of output load current and
observe the resulting output voltage transient. A design
which has good phase margin (
ringing after the output voltage transient returns to its nomi-
nal value.
It should be noted that the stability (phase margin) does not
have to be optimal for the regulator to be stable. The design
analyzed in the previous section was re-compensated by
changing R11 and C10 to intentionally reduce the phase
margin to about 35˚ and re-tested for step response. The
output waveform displayed slight ringing after the initial re-
turn to nominal, but was completely stable otherwise.
In most cases, the compensation components shown in the
Typical Application Circuits will give good performance. To
assist in optimizing phase margin, the following guidelines
show the effects of changing various components.
C
quency of the pole f
loop bandwidth. Increasing C
ing the phase margin) if the loop bandwidth is too wide
(
to the unity-gain crossover frequency.
ESR of C
needed to cancel negative phase shift near the unity-gain
frequency. High-ESR capacitors can not be used, since the
zero will be too low in frequency which will make the loop
bandwidth too wide.
R11/C10: These form a pole and a zero. Changing the value
of C10 changes the frequency of both the pole and zero.
Note that since this causes the frequency of both the pole
and zero to move up or down together, adjusting the value of
C10 does not significantly affect loop bandwidth.
Changing the value of R11 moves the frequency location of
the zero f
(since the value of R11 is much less than the 160 k
impedance of the Gm amplifier). Since only the zero is
moved, this affects both bandwidth and phase margin. This
means adjusting R11 is an easy way to maximize the posi-
tive phase shift provided by the zero. Best results are typi-
cally obtained if f
(where f
Design Procedure
This section presents guidelines for selecting external com-
ponents.
INDUCTOR SELECTION
In selecting an inductor, the parameters which are most im-
portant are inductance, current rating, and DC resistance.
Inductance
>
OUT
F
OSC
: Increasing the capacitance of C
/5) which places the high-frequency poles too close
c
z
is the unity-gain crossover frequency).
(R11), but does not significantly shift the C10 pole
OUT
: The ESR forms a zero f
z
(R11) is in the frequency range of f
p
(C
OUT
IN
, V
) to a lower value and reduces
OUT
OUT
>
can be beneficial (increas-
50˚) will typically show no
, inductor and R
OUT
z
(ESR), which is
moves the fre-
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L
.
c
/4 to f
output
c